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850kHz 700mA Synchronous Buck DC/DC Converter General Description
The AAT1151 SwitchRegTM is a step-down switching converter ideal for applications where high efficiency is required over the full range of output load conditions. The 2.7V to 5.5V input voltage range makes the AAT1151 ideal for single-cell lithiumion/polymer battery applications. Capable of more than 700mA with internal MOSFETs, the currentmode controlled IC provides high efficiency using synchronous rectification. Fully integrated compensation simplifies system design and lowers external parts count. The device operates at a fixed 850kHz switching frequency and enters Pulse Frequency Modulation (PFM) mode for light load current to maintain high efficiency across all load conditions. The AAT1151 is available in Pb-free MSOP-8 and QFN33-16 packages and is rated over the -40C to +85C temperature range.
AAT1151
Features
* * * * * * * * * * * * * * * * * *
SwitchRegTM
VIN Range: 2.7V to 5.5V Up to 95% Efficiency High Initial Accuracy 1% 110m RDS(ON) Internal Switches <1A Shutdown Current 850kHz Switching Frequency Fixed VOUT or Adjustable VOUT 1.0V Integrated Power Switches Synchronous Rectification Current Mode Operation Internal Compensation Stable with Ceramic Capacitors PFM for Optimum Efficiency for All Load Conditions Internal Soft Start Over-Temperature Protection Current Limit Protection MSOP-8 and QFN33-16 Packages -40C to +85C Temperature Range
Applications
* * * * * * * Cellular Phones Digital Cameras MP3 Players Notebook Computers PDAs USB-Powered Equipment Wireless Notebook Adapters
Typical Application
INPUT
10F
VP FB
AAT1151
LX ENABLE 100 VCC
3.0H
OUTPUT SGND 0.1F PGND 2x 22F
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850kHz 700mA Synchronous Buck DC/DC Converter Pin Descriptions
Pin #
MSOP-8 QFN33-16
AAT1151
Symbol
FB
Function
Feedback input pin. This pin is connected to the converter output. It is used to set the output of the converter to regulate to the desired value via an internal resistive divider. For an adjustable output, an external resistive divider is connected to this pin on the 1V model. Signal ground. Connect the return of all small signal components to this pin. (See board layout rules.) Enable input pin. A logic high enables the converter; a logic low forces the AAT1151 into shutdown mode reducing the supply current to less than 1A. The pin should not be left floating. Bias supply. Supplies power for the internal circuitry. Connect to input power via low pass filter with decoupling to SGND. Input supply voltage for the converter power stage. Must be closely decoupled to PGND. Connect inductor to these pins. Switching node internally connected to the drain of both high- and low-side MOSFETs. Main power ground return pin. Connect to the output and input capacitor return. (See board layout rules.) Not internally connected. Exposed paddle (bottom); connect to PGND directly beneath package.
1
4
2 3
5, 6 7
SGND EN
4 5 6, 7 8
9 10, 11, 12 13, 14, 15 1, 2, 3 8, 16 EP
VCC VP LX PGND NC
Pin Configuration
MSOP-8 (Top view) QFN33-16 (Top view)
LX LX LX NC
16 15 14 13
FB SGND EN VCC
1
8
PGND LX LX VP
1
2
7
3
6
PGND PGND PGND FB
1 2 3 4
5 6 7 8
12 11 10 9
VP VP VP VCC
2
4
5
NC EN SGND SGND
2
1151.2007.01.1.6
850kHz 700mA Synchronous Buck DC/DC Converter Absolute Maximum Ratings1
Symbol
VCC, VP VLX VFB VEN TJ VESD
AAT1151
Description
VCC, VP to GND LX to GND FB to GND EN to GND Operating Junction Temperature Range ESD Rating2 - HBM
Value
6 -0.3 to VP + 0.3 -0.3 to VCC + 0.3 -0.3 to 6 -40 to 150 3000
Units
V V V V C V
Thermal Characteristics3
Symbol
JA PD
Description
Thermal Resistance Maximum Power Dissipation (TA = 25C)4 MSOP-8 QFN33-16 MSOP-8 QFN33-16
Value
150 50 667 2.0
Units
C/W mW W
Recommended Operating Conditions
Symbol
T
Description
Ambient Temperature Range
Value
-40 to 85
Units
C
1. Stresses above those listed in Absolute Maximum Ratings may cause permanent damage to the device. Functional operation at conditions other than the operating conditions specified is not implied. Only one Absolute Maximum Rating should be applied at any one time. 2. Human body model is a 100pF capacitor discharged through a 1.5k resistor into each pin. 3. Mounted on a demo board. 4. Derate 6.7mW/C above 25C. 5. Derate 20mW/C above 25C. 1151.2007.01.1.6
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850kHz 700mA Synchronous Buck DC/DC Converter Electrical Characteristics1
VIN = VCC = VP = 5V, TA = -40C to 85C, unless otherwise noted. Typical values are at TA = 25C. Symbol
VIN VOUT VUVLO VUVLO(HYS) IIL IIH IQ ISHDN ILIM RDS(ON)H RDS(ON)L VOUT (VOUT*VIN) VOUT/VOUT FOSC VEN(L) VEN(H) TSD THYS
AAT1151
Description
Input Voltage Range Output Voltage Tolerance Under-Voltage Lockout Under-Voltage Lockout Hysteresis Input Low Current Input High Current Quiescent Supply Current Shutdown Current Current Limit High Side Switch On Resistance Low Side Switch On Resistance Efficiency Load Regulation Line Regulation Oscillator Frequency Enable Threshold Low Enable Threshold High Over-Temperature Shutdown Threshold Over-Temperature Shutdown Hysteresis
Conditions
VIN = VOUT + 0.2 to 5.5V, IOUT = 0 to 700mA VIN Rising VIN Falling VIN = VFB = 5.5V VIN = VFB = 0V No Load, VFB = 0V, VIN = 4.2V TA = 25C VEN = 0V, VIN = 5.5V TA = 25C TA = 25C TA = 25C IOUT = 300mA, VIN = 3.5V VIN = 4.2V, ILOAD = 0 to 700mA VIN = 2.7V to 5.5V TA = 25C
Min
2.7 -3.0
Typ
Max
5.5 +3.0 2.5
Units
V % V mV A A A A A m m % % %/V kHz V V C C
1.2 250 1.0 1.0 300 1.0 1.2 110 100 92 0.9 0.1 850 150 150
210
600 1.4
1200 0.6
140 15
1. The AAT1151 is guaranteed to meet performance specifications over the -40C to +85C operating range and is assured by design, characterization, and correlation with statistical process controls.
4
1151.2007.01.1.6
850kHz 700mA Synchronous Buck DC/DC Converter Typical Characteristics
Efficiency vs. Load Current
(VOUT = 2.5V; L = 4.2H)
100
100 90 80 70 60 50 1 10 100 1000
AAT1151
Efficiency vs. Load Current
(VOUT = 1.8V)
Efficiency (%)
Efficiency (%)
90
2.7V
80
3.6V
4.2V
70
60
50 1 10 100 1000
Output Current (mA)
Load Current (mA)
No Load Supply Current vs. Input Voltage
300 890
Frequency vs. Input Voltage
Supply Current (A)
250 200 150 100 50 0 2.5
T = 85C
Frequency (kHz)
880
T = -40C
T = 25C
870
860
850 3 3.5 4 4.5 5 5.5 2.5 3 3.5 4 4.5 5 5.5
Input Voltage (V)
Input Voltage (V)
Output Voltage vs. Temperature
3.0 1.794 1.792 2.0
Load and Line Regulation
VIN = 4.2V VIN = 3.6V VIN = 2.7V
Output Voltage (V)
VOUT Error (%)
-20 0 20 40 60 80 100
1.79 1.788 1.786 1.784 1.782 1.78 -40
1.0 0.0 -1.0 -2.0 -3.0 1 10 100
1000
Temperature (C)
Load Current (mA)
1151.2007.01.1.6
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850kHz 700mA Synchronous Buck DC/DC Converter Typical Characteristics
Switching Frequency vs. Temperature
1200 20 1000 1.4 1.2
AAT1151
Output Ripple 1.8V, 50mA, VIN = 3.6V Circuit of Figure 1
Output Voltage (AC coupled) (top) (mV)
10 0 -10 -20 -30 -40 -50 -60
Frequency (kHz)
Inductor Current (bottom) (A)
800 600 400 200 0 -40 -20 0 20 40 60 80 100
1 0.8 0.6 0.4 0.2 0 -0.2
Temperature (C)
Time (2s/div)
Line Transient Response 1.8V, 50mA Circuit of Figure 1
Output Voltage (AC coupled) (top) (mV)
4.4 4.2 120 100
Output Ripple 1.8V, 0.7A, VIN = 3.6V Circuit of Figure 1
20 10 0 -10 -20 -30 -40 -50 -60 3.5 3
Inductor Current (bottom) (A)
Output Voltage (bottom) (mV)
Input Voltage (top) (V)
4 3.8 3.6 3.4 3.2 3 2.8
80 60 40 20 0 -20 -40
2.5 2 1.5 1 0.5 0 -0.5
Time (20s/div)
Time (2s/div)
Line Transient Response 1.8V, 0.7A Circuit of Figure 1
4.4 4.2 120 100
Load Transient Response 50mA to 0.7A VIN = 3.6V - Circuit of Figure 1
Output Voltage (top) (mV) (AC coupled)
40 20 0 -20 -40 -60 -80 -100 -120 3.5 3
Inductor Current (bottom) (A)
Output Voltage (bottom) (mV)
Input Voltage (top) (V)
4 3.8 3.6 3.4 3.2 3 2.8
80 60 40 20 0 -20 -40
2.5 2 1.5 1 0.5 0 -0.5
Time (20s/div)
Time (200s/div)
6
1151.2007.01.1.6
850kHz 700mA Synchronous Buck DC/DC Converter Typical Characteristics
Soft Start 1.8V, 0.7A, VIN = 3.6V Circuit of Figure 1
4 3.5 3 20 3 2 1 0 -1 -2 -3 -4
AAT1151
Output Ripple Circuit of Figure 1
Enable (top) Output (middle) (V)
Inductor Current (bottom) (A)
2.5 2 1.5 1 0.5 0 -0.5
15
Ripple (mV)
VIN = 2.7V
10
VIN = 3.6V
5
VIN = 4.2V
0 1 10 100 1000
Time (200s/div)
Output Current (mA)
1151.2007.01.1.6
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850kHz 700mA Synchronous Buck DC/DC Converter Functional Block Diagram
VCC VP = 2.7V to 5.5V
AAT1151
1.0V REF
FB
OP. AMP
CMP
DH
LOGIC
LX
1M
DL Temp. Sensing
OSC
SGND
EN
PGND
Operation
Control Loop
The AAT1151 is a peak current mode buck converter. The inner wide bandwidth loop controls the peak current of the output inductor. The output inductor current is sensed through the P-channel MOSFET (high side) and is also used for short-circuit and overload protection. A fixed slope compensation signal is added to the sensed current to maintain stability. The loop appears as a voltage programmed current source in parallel with the output capacitor. The voltage error amplifier output programs the current loop for the necessary inductor current to force a constant output voltage for all load and line conditions. The voltage feedback resistive divider is internal, dividing the output voltage to the error amplifier reference voltage of 1.0V. The voltage error amplifier does not have the large DC gain typical of most error amplifiers. This eliminates the need for external compensation components, while still providing sufficient DC loop gain for load regulation. The voltage loop crossover frequency and phase margin are set by the output capacitor value only.
PFM/PWM Operation
Light load efficiency is maintained by way of PFM control. The AAT1151 PFM control forces the peak inductor current to a minimum level regardless of load demand. At medium to high load demand, this has no effect on circuit operation and normal PWM controls take over. PFM reduces the switching frequency at light loads, thus reducing the associated switching losses.
Soft Start/Enable
Soft start increases the inductor current limit point in discrete steps when the input voltage or enable input is applied. It limits the current surge seen at the input and eliminates output voltage overshoot. When pulled low, the enable input forces the AAT1151 into a low-power, non-switching state. The total input current during shutdown is less than 1A.
Power and Signal Source
Separate small signal ground and power supply pins isolate the internal control circuitry from the noise associated with the output MOSFET switching. The low pass filter R1 and C2 in schematic Figure 1 filters the noise associated with the power switching.
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850kHz 700mA Synchronous Buck DC/DC Converter
U1 AAT1151-QFN 12 R1 100 R2 100k C2 0.1F R6 100k 11 10 9 7 6 16 5 VP VP VP VCC EN GND N/C GND OUT LX LX LX N/C PGND PGND PGND 4 15 14 13 8 3 2 1
60
AAT1151
Efficiency vs. Load Current
1.8V
100
2.7V-4.2V
(VOUT = 1.8V)
C1 10F
Efficiency (%)
L1 3.3H C3, C4 2x22F
90
2.7V
80
3.6V
4.2V
70
C1 Murata 10F 6.3V X5R GRM42-6X5R106K6.3 C3-C4 MuRata 22F 6.3V GRM21BR60J226ME39L X5R 0805 L1 Sumida CDRH3D16-4R7NC or CDRH3D16-3R3NC
50 1 10 100 1000
Load Current (mA)
Figure 1: AAT1151 Evaluation Board.
Current Limit and Over-Temperature Protection
For overload conditions, the peak input current is limited. As load impedance decreases and the output voltage falls closer to zero, more power is dissipated internally, raising the device temperature. Thermal protection completely disables switching when internal dissipation becomes excessive, protecting the device from damage. The junction over-temperature threshold is 140C with 10C of hysteresis.
peak and average current ratings yet result in excessive losses due to a high DCR. Always consider the losses associated with the DCR and its effect on the total converter efficiency when selecting an inductor. For a 1.0A load and the ripple set to 40% at the maximum input voltage, the maximum peak-topeak ripple current is 280mA. The inductance value required is 2.84H.
VOUT VOUT L=I *k*F * 1- V O S IN = 1.5V * 1 - 1.5V 4.2V 1A * 0.4 * 850kHz
Inductor
The output inductor is selected to limit the ripple current to some predetermined value, typically 20% to 40% of the full load current at the maximum input voltage. Manufacturer's specifications list both the inductor DC current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturation characteristics. The inductor should not show any appreciable saturation under normal load conditions. During overload and transient conditions, the average current in the inductor can meet or exceed the current limit point of the AAT1151. These conditions can tolerate greater saturation in the inductor without degradation in converter performance. Some inductors may meet the
= 2.84H
The factor "k" is the fraction of full load selected for the ripple current at the maximum input voltage. For ripple current at 40% of the full load current, the peak current will be 120% of full load. Selecting a standard value of 3.0H gives 38% ripple current. A 3.0H inductor selected from the Sumida CDRH5D28 series has a 24m DCR and a 2.4A DC current rating. At full load, the inductor DC loss is 24mW, which amounts to a 1.6% loss in efficiency.
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850kHz 700mA Synchronous Buck DC/DC Converter
Input Capacitor
The primary function of the input capacitor is to provide a low impedance loop for the edges of pulsed current drawn by the AAT1151. A low ESR/ESL ceramic capacitor is ideal for this function. To minimize stray inductance, the capacitor should be placed as close as possible to the IC. This keeps the high frequency content of the input current localized, minimizing radiated and conducted EMI while facilitating optimum performance of the AAT1151. Ceramic X5R or X7R capacitors are ideal for this function. The size required will vary depending on the load, output voltage, and input voltage source impedance characteristics. A typical value is around 10F. The input capacitor RMS current varies with the input voltage and the output voltage. The equation for the RMS current in the input capacitor is:
VO V * 1- O VIN VIN
VOUT * (VIN - VOUT) L * FS * VIN 2* 3 * 1
AAT1151
IRMS =
For a ceramic capacitor, the ESR is so low that dissipation due to the RMS current of the capacitor is not a concern. Tantalum capacitors with sufficiently low ESR to meet output voltage ripple requirements also have an RMS current rating well beyond that actually seen in this application.
Layout
Figures 2 through 5 display the suggested PCB layout for the AAT1151. The following guidelines should be used to help ensure a proper layout. * * * The input capacitor (C1) should connect as closely as possible to VP (Pin 5) and PGND (Pin 8). C2 and L1 should be connected as closely as possible. The connection L1 to the LX node should be as short as possible. The feedback trace (Pin 1) should be separate from any power trace and connect as closely as possible to the load point. Sensing along a high-current load trace will degrade DC load regulation. The resistance of the trace from the load return to the PGND (Pin 8) should be kept to a minimum. This will help to minimize any error in DC regulation due to differences in the potential of the internal signal ground and the power ground. Low pass filter R1 and C3 provide a cleaner bias source for the AAT1151 active circuitry. C3 should be placed as closely as possible to SGND (Pin 2) and VCC (Pin 4). See Figures 2 and 7.
IRMS = IO *
The input capacitor RMS ripple current reaches a maximum when VIN is two times the output voltage where it is approximately one half of the load current. Losses associated with the input ceramic capacitor are typically minimal and are not an issue. Proper placement of the input capacitor can be seen in the reference design layout in Figures 2 and 4.
*
Output Capacitor
Since there are no external compensation components, the output capacitor has a strong effect on loop stability. Lager output capacitance will reduce the crossover frequency with greater phase margin. For the 1.5V 1A design using the 4.1H inductor, two 22F capacitors provide a stable output. In addition to assisting stability, the output capacitor limits the output ripple and provides holdup during large load transitions. The output capacitor RMS ripple current is given by: *
10
1151.2007.01.1.6
850kHz 700mA Synchronous Buck DC/DC Converter
AAT1151
Figure 2: MSOP Evaluation Board Top Layer.
Figure 3: MSOP Evaluation Board Bottom Layer.
Figure 4: QFN Evaluation Board Top Side.
Figure 5: QFN Evaluation Board Bottom Side.
45 40 35 30
R4=10k
2.7V - 5.5V 5 R1 100 R2 100k C1 10F C3 0.1F 4 3 2 AAT1151-1.0 VP VCC EN FB LX LX 1 7 6 8
VO+ 1.25V 0.7A R3 2.55k 1%
R3 (k)
25 20 15 10 5 0 1 1.5 2 2.5 3 3.5 4 4.5 5 5.5
L1 3.3H R4 10k 1%
C2, C4 2x 22F
GND PGND
VC1 Murata 10F 6.3V X5R GRM42-6X5R106K6.3 C2, C4 MuRata 22F 6.3V GRM21BR60J226ME39L X5R 0805 L1 Sumida CDRH3D16-3R3 NC
Output Voltage (V)
Figure 6: R3 vs. VOUT for Adjustable Output Using the AAT1151-1.0V.
Figure 7: Adjustable Output Schematic.
1151.2007.01.1.6
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850kHz 700mA Synchronous Buck DC/DC Converter
Thermal Calculations
There are two types of losses associated with the AAT1151 output switching MOSFET: switching losses and conduction losses. Conduction losses are associated with the RDS(ON) characteristics of the output switching device. At the full load condition, assuming continuous conduction mode (CCM), a simplified form of the total losses is given by:
AAT1151
Once the total losses have been determined, the junction temperature can be derived from the JA for the MSOP-8 package.
TJ = P * JA + TAMB
Adjustable Output
For applications requiring an output other than the fixed available, the 1V version can be programmed externally. Resistors R3 and R4 of Figure 7 force the output to regulate higher than 1 volt. R4 should be 100 times less than the 1M internal resistance of the FB pin (recommended 10k). Once R4 is selected, R3 can be calculated. For a 1.25 volt output with R4 set to 10.0k, R3 is 2.55k.
P=
IO2 * (RDS(ON)H * VO + RDS(ON)L * (VIN * VO)) V IN
+ (t SW * FS * I O * VIN + IQ) * VIN
where Iq is the AAT1151 quiescent current.
R3 = (VO - 1) * R4 = 0.25 * 10k = 2.55k
12
1151.2007.01.1.6
850kHz 700mA Synchronous Buck DC/DC Converter
Design Example
Specifications IOUT IRIPPLE VOUT VIN FS TAMB 0.7A 40% of Full Load at Max VIN 1.5V 2.7V to 4.2V (3.6V nominal) 850kHz 85C
AAT1151
Maximum Input Capacitor Ripple
I RMS = I O * VO V * 1 - O = 0.35Arms, VIN = 2 * VO VIN VIN
P = esr * IRMS2 = 5m * 0.352 A = 0.6mW
Inductor Selection
L=
V VOUT 1.5V 1.5V 1 - OUT = 1= 4.05H IO k FS VIN 0.7A 0.4 850kHz 4.2V
Select Sumida inductor CDRH3D16 3.3H 63m 1.8mm height.
I =
1.5V VO V 1.5V 1- O = 1= 340mA VIN 3.3H 850kHz 4.2V L FS
IPK = IOUT +
I = 0.7A + 0.17A = 0.87A 2
P = IO2 DCR = (0.7)2 63m = 31mW
Output Capacitor Ripple Current
IRMS = VOUT * (VIN - VOUT) 1 1.5V * (4.2V - 1.5V) * = 99mArms = L * FS * VIN 2 * 3 3.3H * 850kHz * 4.2V 2* 3 1 *
Pesr = esr * IRMS2 = 5m * 992 mA = 50W
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850kHz 700mA Synchronous Buck DC/DC Converter
AAT1151 Dissipation
PTOTAL = IO2 * (RDS(ON)H * VO + RDS(ON)L * (VIN -VO)) VIN + (tsw * FS * IO + IQ) * VIN
AAT1151
=
(0.7A)2 * (0.2 * 1.5V + 0.187 * (4.2V - 1.5V))
4.2V
+ (20nsec * 850kHz * 0.7A + 0.3mA) * 4.2V = 0.145W
TJ(MAX) = TAMB + JA * PLOSS = 85C + 150C/W * 0.145W = 107C (MSOP-8)
= 85C + 50C/W * 0.145W = 92C (QFN33-16)
Manufacturer
TaiyoYuden Toko Sumida Sumida Sumida MuRata MuRata MuRata
Part Number
NPO5DB4R7M A914BYW-3R5M-D52LC CDRH5D28-3R0 CDRH5D28-4R2 CDRH5D18-4R1 LQH55DN4R7M03 LQH66SN4R7M03 CDRH3D16-3R3
Value
4.7H 3.5H 3.0H 4.2H 4.1H 4.7H 4.7H 3.3H
Max DC Current
1.4A 1.34A 2.4A 2.2A 1.95A 2.7A 2.2A 1.1A
DCR ()
0.038 0.073 0.024 0.031 0.057 0.041 0.025 0.063
Size (mm) LxWxH
5.9 5.0 5.7 5.7 5.7 5.0 6.3 3.8 x x x x x x x x 6.1 5.0 5.7 5.7 5.7 5.0 6.3 3.8 x x x x x x x x 2.8 2.0 3.0 3.0 2.0 4.7 4.7 1.8
Type
Shielded Shielded Shielded Shielded Shielded Non-Shielded Shielded Shielded
Table 1: Surface Mount Inductors.
Manufacturer
MuRata MuRata MuRata MuRata
Part Number
GRM40 X5R 106K 6.3 GRM42-6 X5R 106K 6.3 GRM21BR60J226ME39L GRM21BR60J106ME39L
Value
10F 10F 22F 10F
Voltage
6.3V 6.3V 6.3V 6.3V
Temp. Co.
X5R X5R X5R X5R
Case
0805 1206 0805 0805
Table 2: Surface Mount Capacitors.
14
1151.2007.01.1.6
850kHz 700mA Synchronous Buck DC/DC Converter Ordering Information
Output Voltage1
1.0V (Adj VOUT 1.0V) 1.0V (Adj VOUT 1.0V) 1.8V 1.8V 2.5V 2.5V 3.3V
AAT1151
Package
MSOP-8 QFN33-16 MSOP-8 QFN33-16 MSOP-8 QFN33-16 MSOP-8
Marking2
JHXYY JHXYY JIXYY JIXYY JJXYY JJXYY NKXYY
Part Number (Tape and Reel)3
AAT1151IKS-1.0-T1 AAT1151IVN-1.0-T1 AAT1151IKS-1.8-T1 AAT1151IVN-1.8-T1 AAT1151IKS-2.5-T1 AAT1151IVN-2.5-T1 AAT1151IKS-3.3-T1
All AnalogicTech products are offered in Pb-free packaging. The term "Pb-free" means semiconductor products that are in compliance with current RoHS standards, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. For more information, please visit our website at http://www.analogictech.com/pbfree.
Package Information4
MSOP-8
4 4 1.95 BSC
3.00 0.10
4.90 0.10
0.60 0.20 PIN 1 0.254 BSC
0.95 REF
3.00 0.10 10 5
0.95 0.15 0.85 0.10
0.075 0.075 0.65 BSC 0.30 0.08
All dimensions in millimeters. 1. Contact local sales office for custom options. 2. XYY = assembly and date code. 3. Sample stock is generally held on part numbers listed in BOLD. 4. The leadless package family, which includes QFN, TQFN, DFN, TDFN and STDFN, has exposed copper (unplated) at the end of the lead terminals due to the manufacturing process. A solder fillet at the exposed copper edge cannot be guaranteed and is not required to ensure a proper bottom solder connection. 1151.2007.01.1.6
GAUGE PLANE
0.155 0.075
15
850kHz 700mA Synchronous Buck DC/DC Converter
QFN33-16
AAT1151
Pin 1 Identification
1
0.230 0.05
5
3.000 0.05
C0.3
0.400 0.100
Pin 1 Dot By Marking
13 9
3.000 0.05
0.500 0.05
Top View
Bottom View
1.70 0.05
0.214 0.036
0.025 0.025
Side View
All dimensions in millimeters.
(c) Advanced Analogic Technologies, Inc. AnalogicTech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an AnalogicTech product. No circuit patent licenses, copyrights, mask work rights, or other intellectual property rights are implied. AnalogicTech reserves the right to make changes to their products or specifications or to discontinue any product or service without notice. Customers are advised to obtain the latest version of relevant information to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale supplied at the time of order acknowledgement, including those pertaining to warranty, patent infringement, and limitation of liability. AnalogicTech warrants performance of its semiconductor products to the specifications applicable at the time of sale in accordance with AnalogicTech's standard warranty. Testing and other quality control techniques are utilized to the extent AnalogicTech deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed. AnalogicTech and the AnalogicTech logo are trademarks of Advanced Analogic Technologies Incorporated. All other brand and product names appearing in this document are registered trademarks or trademarks of their respective holders.
Advanced Analogic Technologies, Inc.
830 E. Arques Avenue, Sunnyvale, CA 94085 Phone (408) 737- 4600 Fax (408) 737- 4611 16
1151.2007.01.1.6
0.900 0.100

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